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Application Notes

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  Power Gain Stages for Monolithic Amplifiers &mdash AN18
  PDF, 2.5 Mb, File published: Mar 1, 1986
  This note presents output state circuits which provide power gain for monolithic amplifiers. The circuits feature voltage gain, current gain, or both. Eleven designs are shown, and performance is summarized. A generalized method for frequency compensation appears in a separate section.
  Extract from the document

  Application Note 18
  March 1986
  Power Gain Stages for Monolithic Amplifiers
  Jim Williams
  Most monolithic amplifiers cannot supply more than a few
  hundred milliwatts of output power. Standard IC processing
  techniques set device supply levels at 36V, limiting available output swing. Additionally, supplying currents beyond
  tens of milliamperes requires large output transistors and
  causes undesirable IC power dissipation.
  Many applications, however, require greater output power
  than most monolithic amplifiers will deliver. When voltage
  or current gain (or both) is needed, a separate output
  stage is necessary. The power gain stage, sometimes
  called a “booster”, is usually placed within the monolithic
  amplifier’s feedback loop, preserving the IC’s low drift and
  stable gain characteristics. 150mA Output Stage
  Figure 1a shows the LTВ®1010 monolithic 150mA current
  booster placed within the feedback loop of a fast FET
  amplifier. At lower frequencies, the buffer is within the
  feedback loop so that its offset voltage and gain errors
  are negligible. At higher frequencies, feedback is through
  Cf, so that phase shift from the load capacitance acting
  against the buffer output resistance does not cause loop …

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  Composite Amplifiers &mdash AN21
  PDF, 330 Kb, File published: Jul 1, 1986
  Applications often require an amplifier that has extremely high performance in several areas. For example, high speed and DC precision are often needed. If a single device cannot simultaneously achieve the desired characteristics, a composite amplifier made up of two (or more) devices can be configured to do the job. AN21 shows examples of composite approaches in designs combining speed, precision, low noise and high power.
  Extract from the document

  Application Note 21
  July 1986
  Composite Amplifiers
  Jim Williams
  Amplifier design, regardless of the technology utilized, is
  a study in compromise. Device limitations make it difficult
  for a particular amplifier to achieve optimal speed, drift,
  bias current, noise and power output specifications. As
  such, various amplifier families emphasizing one or more
  of these areas have evolved. Some amplifiers are very good
  attempts at doing everything well, but the best achievable
  performance п¬Ѓgures are limited to dedicated designs. designed with little attention to DC biasing considerations
  if a separate stabilizing stage is employed.
  Figure 1 shows a composite made up of an LTВ®1012 low drift
  device and an LT1022 high speed amplifier. The overall circuit is a unity-gain inverter, with the summing node located
  at the junction of three 10k resistors. The LT1012 monitors
  this summing node, compares it to ground and drives the
  LT1022’s positive input, completing a DC stabilizing loop
  around the LT1022. The 10k-300pF time constant at the
  LT1012 limits its response to low frequency signals. The
  LT1022 handles high frequency inputs while the LT1012
  stabilizes the DC operating point. The 4.7k-220О© divider
  at the LT1022 prevents excessive input overdrive during …

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  Converting Light to Digits: LTC1099 Half Flash 8-Bit A/D Converter Digitizes Photodiode Array &mdash AN33
  PDF, 703 Kb, File published: Mar 2, 1989
  This application note describes a Linear Technology "Half-Flash" A/D converter, the LTC1099, being connected to a 256 element line scan photodiode array. This technology adapts itself to handheld (i.e., low power) bar code readers, as well as high resolution automated machine inspection applications.
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  Bridge Circuits &mdash AN43
  PDF, 3.8 Mb, File published: Jun 1, 1990
  Subtitled "Marrying Gain and Balance," this note covers signal conditioning circuits for various types of bridges. Included are transducer bridges, AC bridges, Wien bridge oscillators, Schottky bridges, and others. Special attention is given to amplifier selection criteria. Appended sections cover strain gauge transducers, understanding distortion measurements, and historical perspectives on bridge readout mechanisms and Wein bridge oscillators.
  Extract from the document

  Application Note 43
  June 1990
  Bridge Circuits
  Marrying Gain and Balance
  Jim Williams
  Bridge circuits are among the most elemental and powerful
  electrical tools. They are found in measurement, switching, oscillator and transducer circuits. Additionally, bridge
  techniques are broadband, serving from DC to bandwidths
  well into the GHz range. The electrical analog of the mechanical beam balance, they are also the progenitor of all
  electrical differential techniques. and stability of the basic configuration. In particular, transducer manufacturers are quite adept at adapting the bridge
  to their needs (see Appendix A, “Strain Gauge Bridges”).
  Careful matching of the transducer’s mechanical characteristics to the bridge’s electrical response can provide a
  trimmed, calibrated output. Similarly, circuit designers
  have altered performance by adding active elements (e.g.,
  amplifiers) to the bridge, excitation source or both. Resistance Bridges
  Figure 1 shows a basic resistor bridge. The circuit is
  usually credited to Charles Wheatstone, although S. H.
  Christie, who demonstrated it in 1833, almost certainly
  preceded him.1 If all resistor values are equal (or the two
  sides ratios are equal) the differential voltage is zero. The
  excitation voltage does not alter this, as it affects both
  sides equally. When the bridge is operating off null, the
  excitation’s magnitude sets output sensitivity. The bridge …

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  Using the LTC Op Amp Macromodels &mdash AN48
  PDF, 297 Kb, File published: Nov 8, 1991
  LTC's op amp macromodels are described in detail, along with the theory behind each model and complete schematics of each topology. Extended modeling topics are discussed, such as phase/frequency response modifications and asymmetric slew rate for JFET op amp models. LTC's macromodels are optimized for accuracy and fast simulation times. Simulation times can be further reduced by using streamlining techniques found throughout AN48.
  Extract from the document

  Application Note 48
  November 1991
  Using the LTC Op Amp Macromodels
  Getting the Most from SPICE and the LTC Library
  Walt Jung INTRODUCTION This application note is an overview discussion of the
  Linear Technology SPICE macromodel library. It assumes
  little if any prior knowledge of this software library or its
  history. However, it does assume familiarity with both the
  analog simulation program SPICE (or one of its many
  derivatives), and modern day op amps, including bipolar,
  JFET, and MOSFET amplifier technologies.
  Some Preliminary SPICE Facts of Life
  In the past few years, SPICE simulations have really begun
  to capture a high level of attention on the part of analog
  circuit designers. Perhaps this is due to more affordable
  high performance computers, or perhaps the time for
  simulation is now upon us. In any event, the bottom line is
  that IC vendors are now making macromodels for op amps
  available to their customers.
  For the analog circuit designer, there can be no better fate
  for simulations, viewing this situation in terms of which
  model to use. Designers no longer need worry about
  whether the third party supplier’s model can really cut it. …

Design Notes

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  Updated Operational Amplifier Selection Guide for Optimum Noise Performance &mdash DN140
  PDF, 74 Kb, File published: Oct 1, 1996
  Extract from the document

  Operational Amplifier Selection Guide for
  Optimum Noise Performance – Design Note 140
  Frank Cox
  Eight years ago, George Erdi wrote a very useful Design
  Note (DN6) that presented information to aid in the
  selection of op amps for optimum noise performance,
  in both graphical and tabular form. Design Note 140 is
  an update of DN6. It covers new low noise op amps as
  well as some high speed op amps. Although a great deal
  has changed in eight years, especially in electronics,
  noise is still a critical issue in op amp circuit design
  and the LTВ®1028 is still the lowest noise op amp for
  low source impedance applications.
  The amount of noise an op amp circuit will produce
  is determined by the device used, the total resistance
  in the circuit, the bandwidth of the measurement, the
  temperature of the circuit and the gain of the circuit. A
  convenient п¬Ѓgure of merit for the noise performance
  of an op amp is the spectral density or spot noise. This
  is obtained by normalizing the measurement to a unit
  of bandwidth. Here the unit is 1Hz and the noise is reported as “nV/√Hz.” The noise in a particular application
  bandwidth can be calculated by multiplying the spot
  noise by the square root of the application bandwidth. …

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  Noise Calculations in Op Amp Circuits &mdash DN15
  PDF, 224 Kb, File published: Sep 1, 1988
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  Noise Calculations1 in Op Amp Circuits – Design Note 15
  Alan Rich
  Noise calculations in op amp circuits are one of the most
  confused calculations that an analog engineer must
  perform.
  One cannot just look at noise specifications; the total op
  amp circuit including resistors and operating frequency
  range must be included in calculations for circuit noise. A
  “low” noise amplifier in one circuit will become a “high”
  noise amplifier in another circuit.
  As part of this Design Note, an IBM-PC2 or compatible
  computer program, NOISE, has been written to perform
  the noise calculations. This program allows the user to
  calculate circuit noise using LTC op amps, determine the
  best LTC op amp for a low noise application, display the
  noise data for LTC op amps, calculate resistor noise, and
  calculate circuit noise using noise specs for any op amp.
  At the end of this Design Note there are detailed operating
  instructions for the computer program NOISE.
  To calculate noise for an op amp circuit, one must consider the op amp voltage and current noise density and
  1/f corner frequency, the frequency range of interest, and
  the resistor noise.
  The most comprehensive specification for voltage or current noise is the noise density frequency response curve …

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  Operational Amplifier Selection Guide for Optimum Noise Performance &mdash DN3
  PDF, 224 Kb, File published: Oct 1, 1987
  Extract from the document

  Operational Amplifier Selection Guide for Optimum Noise
  Performance – Design Note 3
  George Erdi
  The LTВ®1028 is the lowest noise op amp available today.
  Its voltage noise is less than that of a 50О© resistor. In
  other words, if the LT1028 is operated with source resistors in excess of 50О© , resistor noise will dominate. If the
  application requires large source resistors, the LT1028’s
  relatively high current noise will limit performance, and
  other op amps will provide lower overall noise. The table below lists which op amp gives minimum total
  noise for a specified equivalent source resistance. A two
  step procedure should be followed to optimize noise: In general, the total noise of any op amp (referred to the
  input) is given by: The table actually has two sets of devices: one for low
  frequency (instrumentation), one for wideband applications. The slight differences between the two columns
  occur because voltage and current noise increase at low
  frequencies (below the so-called 1/f corner) while resistor
  noise is flat with frequency. total noise = (voltage noise) + (resistor noise) + (current noise R )
  2 2 2 eq where, (2) Enter the table to find the optimum op amp. Best Op Amp for Lowest Noise vs Source Resistance resistor noise = 0.13 Re q in nV Hz
  and Req = equivalent source resistance
  = R2 + R1//R3
  R3
  R1 – R2 + DN003 F01 Several conclusions can be reached by inspection of the
  equation:
  (a) To minimize noise, resistor values should be minimized to make the contribution of the second and …

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  Operational Amplifier Selection Guide for Optimum Noise Performance &mdash DN6
  PDF, 137 Kb, File published: Jan 1, 1988
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  A 1mV Offset, Clock-Tunable, Monolithic 5-Pole Lowpass Filter &mdash DN67
  PDF, 73 Kb, File published: Feb 1, 1993
  Extract from the document

  A 1mV Offset, Clock-Tunable, Monolithic 5-Pole
  Lowpass Filter -Design Note 67
  Nello Sevastopoulos
  The LTC В®1063 is the п¬Ѓrst monolithic lowpass п¬Ѓlter
  simultaneously offering outstanding DC and AC performance. It features internal or external clock tunability,
  cutoff frequencies up to 50kHz, 1mV typical output DC
  offset, and a dynamic range in excess of 12 bits for over
  a decade of input voltage.
  The LTC1063 approximates a 5-pole Butterworth lowpass п¬Ѓlter. The unique internal architecture of the п¬Ѓlter
  allows outstanding amplitude matching from device to
  device. Typical matching ranges from 0.01dB at 25%
  of the п¬Ѓlter passband to 0.05dB at 50% of the п¬Ѓlter
  passband. This capability is important for multichannel
  data-acquisition systems where channel-to-channel
  matching is critical.
  Using the Filter’s Internal Oscillator
  An internal or external clock programs the filter’s cutoff
  frequency. The clock-to-cutoff frequency ratio is 100:1.
  In the absence of an external clock, the LTC1063’s internal precision oscillator can be used. An external resistor
  and capacitor set the device’s internal clock frequency
  (Figure 1). The internal oscillator output is brought out
  VIN 1 1 3 –5V
  0.1ОјF 7 …

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